<![CDATA[ IEEE Transactions on Antennas and Propagation - new TOC ]]>
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TOC Alert for Publication# 8 2018March 19<![CDATA[Table of contents]]>663C11055229<![CDATA[IEEE Transactions on Antennas and Propagation]]>663C2C283<![CDATA[Wideband Reflector-Backed Folded Bowtie Antenna for Ground Penetrating Radar]]>$le$ 2, a broadside gain between 5 and 12 dBi, for total antenna size of $1.4lambda _{m} times lambda _{m}$ , $lambda _{m}$ free space wavelength at the center frequency, are achieved as confirmed by laboratory-controlled measurements in free space and in GPR settings.]]>663105610632811<![CDATA[Bandwidth Enhancement of Low-Profile Microstrip Antenna for MIMO Applications]]>663106410757400<![CDATA[Systematic Design of a Multiport MIMO Antenna With Bilateral Symmetry Based on Characteristic Mode Analysis]]>$times ,, 61.5$ mm $times ,, 10$ mm ($0.4lambda _{0} times 0.49lambda _{0} times 0.08lambda _{0} $ at 2.4 GHz). The measurements demonstrate that these antennas have a low mutual coupling (<−20 dB) and a low envelope correlation coefficient (<0.04).]]>663107610853769<![CDATA[Low-Profile EndFire Leaky-Wave Antenna With Air Media]]>$lambda _{0}$ /4 ($lambda _{0}$ is the wavelength in free space) to achieve a relatively wide impedance bandwidth. A prototype of the proposed endfire antenna is fabricated and tested. The measured results are consistent with full-wave simulation results. The length of the whole leaky-wave array is about $6lambda _{0}$ , and the measured gain in the endfire direction is 11.5 dBi at 5.1 GHz.]]>663108610922608<![CDATA[Self-Curing Decoupling Technique for Two Inverted-F Antennas With Capacitive Loads]]>663109311012735<![CDATA[Efficient Excitation of Characteristic Modes for Radiation Pattern Control by Using a Novel Balanced Inductive Coupling Element]]>$P_{{{reac}}}$ ) stored in the near-field zone and hence maximizes the amount of the radiated power ($P_{r}$ ). To better highlight the benefits offered by the presented approach, a set of BIEs is applied on a platform to obtain a fully reconfigurable radiation pattern. The evaluation of the $P_{{{reac}}}$ , $P_{r}$ , and equivalent isotropically radiated power provided by the BIE reveals the importance of a pure modal excitation. To assess the reliability of the proposed BIEs, some prototypes have been manufactured and tested.]]>663110211133055<![CDATA[Matched, Low-Loss, and Wideband Graded-Index Flat Lenses for Millimeter-Wave Applications]]>663111411233811<![CDATA[Low-Profile Planar Filtering Dipole Antenna With Omnidirectional Radiation Pattern]]>663112411322323<![CDATA[Design and Experiments of Bandwidth-Controllable Broadband Monopole Antennas With Conformal Anisotropic Impedance Surface Coatings]]>663113311423836<![CDATA[Microstrip Magnetic Monopole and Dipole Antennas With High Directivity and a Horizontally Polarized Omnidirectional Pattern]]>$2lambda $ due to high-order resonant mode interference. A solution is provided to suppress the second resonant mode and retain the radiation peak in the azimuth direction. The peak gain of the microstrip magnetic monopole is increased to 7.2 dBi when the antenna length is approximately $3lambda $ . A microstrip magnetic dipole antenna with an antenna length of $6lambda $ is also designed to obtain a higher gain of 9.7 dBi. The impedance bandwidths of the microstrip magnetic monopole and dipole antennas are 6.5% (2.37–2.52 GHz) and 7.3% (2.35–2.53 GHz), respectively. The proposed antennas produce maximum radiation in the azimuth direction and have horizontally polarized omnidirectional patterns in the azimuth plane.]]>663114311523374<![CDATA[Experimental Validation of a Ku-Band Dual-Circularly Polarized Metasurface Antenna]]>11 modes are excited with ±90° phase shift, which determine the right-hand or left-hand sense of the broadside beam generated by the MTS. Manufacturing details of the MTS and excitations are given, and the measurements are compared with the simulation results. Finally, conclusions are drawn.]]>663115311592950<![CDATA[Orthomode Transducers With Folded Double-Symmetry Junctions for Broadband and Compact Antenna Feeds]]>663116011683159<![CDATA[Systematic Design of THz Leaky-Wave Antennas Based on Homogenized Metasurfaces]]>663116911782358<![CDATA[Wideband Low-Profile SIW Cavity-Backed Circularly Polarized Antenna With High-Gain and Conical-Beam Radiation]]>$0.062lambda _{0}$ , a 10 dB impedance bandwidth of 20.4%, a 3 dB AR bandwidth of 17%, a maximum gain of 8.25 dBic, and an advantage of large ground compatibility.]]>663117911883160<![CDATA[Omnidirectional Dielectric Resonator Antenna With a Planar Feed for Circular Polarization Diversity Design]]>$_{01delta }$ mode by a planar shorted microstrip cross. With this nonintrusive feed, the DRA can be fabricated without the need of drilling a hole in the DR as required in the probe feed method. This DRA is applied to the first omnidirectional circularly polarized (CP) diversity DRA. To generate omnidirectional CP fields, the TM$_{01delta }$ and TE$_{011+delta }$ modes are excited simultaneously. The TE$_{011+delta }$ mode is excited by four microstrip arcs. They provide a pair of equivalent magnetic dipoles that generate fields that are orthogonal to those of the TM$_{01delta }$ mode. Omnidirectional CP fields can be obtained when the (orthogonal) fields of the TM$_{01delta }$ and TE$_{011+delta }$ modes are equal in amplitude but in phase quadrature. In our two-port CP diversity design, phase differences of +90° and −90° are obtained in ports 1 and 2 to generate right- and left-hand CP fields, respectively. Prototypes at ~2.4 GHz were designed, fabricated, and measured for WLAN applications. The S-parameters, radiation patterns, antenna gains, and efficiencies are studied. For the diversity design, the axial ratio, envelope correlation coefficient, and mean effective gain are also obtained. The measured and simulation results are in reasonable agreement.]]>663118911972907<![CDATA[Fast Pattern Calculation of Rib Reflectors With Varying Surface Distortions]]>663119812071923<![CDATA[A Compact and High-Gain Cavity-Backed Waveguide Aperture Antenna in the C-Band for High-Power Applications]]>$times86$ mm (width) $times48$ mm (height), the proposed antenna is also ultracompact in comparison with other reported antennas with the same aperture size and electromagnetic features. The compactness of the proposed antenna was accomplished by employing a novel approach to excite the output aperture. This approach was achieved by incorporating the cavity-backed waveguide apertures and waveguide steps. The antenna structure is composed of three aluminum layers firmly screwed to each other. Each layer is manufactured by using the computer numerical control milling machine. The proposed antenna is an appropriate candidate for high-power applications due to its metallic structure and high radiation efficiency. The proposed structure is very robust and has carefully been designed to exhibit low sensitive to manufacturing tolerances.]]>663120812162711<![CDATA[Parallel Dual-Loop Antenna for WWAN/LTE Metal-Rimmed Smartphone]]>$2 times 2$ multi-in multi-out antenna system) is also demonstrated, and its performances are acceptable for smartphone applications.]]>663121712263936<![CDATA[Optimized Corrugated Tapered Slot Antenna for mm-Wave Applications]]>663122712356115<![CDATA[Phase-Delay Versus Phase-Rotation Cells for Circular Polarization Transmit Arrays—Application to Satellite Ka-Band Beam Steering]]>663123612473247<![CDATA[An Electronically Tunable Biomimetic Antenna Array]]>663124812573117<![CDATA[Fast and Accurate Modeling of Dual-Polarized Reflectarray Unit Cells Using Support Vector Machines]]>663125812702705<![CDATA[Compensation for Waveguide Losses in the Design of Slot Arrays]]>663127112791310<![CDATA[D-Band High-Gain Circular-Polarized Plate Array Antenna]]>$2 times 2$ subarray antenna is proposed at first, consisting of integrated horns, complementary phase shifters, and a dual-polarized power divider (PD). The complementary phase shifter includes a parallel capacitance phase shifter and a parallel inductance phase shifter. Phase shifts generated by inductance and capacitance structures present opposite tendencies versus frequency. Therefore, an appropriate combination of them will make the phase shift almost constant over a wideband, which is important to generate a wideband CP beam. Besides, the capacitance phase shifter can be implemented by inserting irises at waveguide broadsides, while the inductance phase shifter can be achieved by inserting irises at the waveguide narrow side. Such a simple configuration can guarantee the element spacing limitation and the fabrication accuracy. The dual-polarized PD consists of an octagon cavity with rotated symmetrical coupling slots for wideband equal-amplitude and in-phase outputs. In addition, some matching layers and matching ridges in the octagon cavity are introduced to achieve wideband matching. Finally, a wideband array feeding network is used to build a $16 times 16$ -element left-handed CP array antenna. The $S_{11}$ below −10 dB bandwidth is about 15.1%, and the co-gain is more than 30 dBi from 130 to 149 GHz. The radiation efficiency is higher than 65% and a 3 dB axial ratio can be satisfied over the whole band.]]>663128012873009<![CDATA[Dual Circular-Polarized SIW-Fed High-Gain Scalable Antenna Array for 60 GHz Applications]]>$8 times 8$ element array is designed to demonstrate its function, and the simulated data exhibit an overlapped bandwidth (SWR < 2, 3 dB down gain bandwidth and AR < 3 dB) of approximately 23%, a gain up to 25.8 dBic for both ports, and a port-to-Port isolation larger than 14 dB. Good unidirectional and symmetrical radiation patterns are observed. A prototype is fabricated, and the measured results agree with the simulated ones with acceptable disparities. The reported structure is built by the conventional printed circuit board technology which is cost effective. With these advantages, the proposed scalable antenna design is a good candidate for millimeter-wave wireless communications.]]>663128812984652<![CDATA[Planar Millimeter-Wave 2-D Beam-Scanning Multibeam Array Antenna Fed by Compact SIW Beam-Forming Network]]>$4 times 4$ Butler matrix (BM). The key point of this design is to propose an E-plane $4 times 4$ BM which realizes a planar E-plane sub-BFN. These two sets of sub-BFNs can joint directly without resorting to any connectors or connecting networks to form such a compact 16-way BFN with a reduced area of merely $3lambda times 12lambda $ . After that, to be compatible with the proposed BFN, a ladder-type $4 times 4$ slot antenna array is employed, which is comprised of four linear $1 times 4$ slot antenna arrays. Different from traditional array, the four subarrays are distributed in separate layers for the purpose of jointing to the BFN more conveniently. Transition network are also required to connect the BFN with the antenna array. Finally, a compact 2-D scanning multibeam array antenna based on the planar SIW BFN are fabricated and measured, which would be an attractive candidate for 5G application.]]>663129913106020<![CDATA[Numerical and Experimental Assessment of Source Reconstruction for Very Near-Field Measurements With an Array of $H$ -Field Probes]]>663131113201973<![CDATA[Susceptibility Derivation and Experimental Demonstration of Refracting Metasurfaces Without Spurious Diffraction]]>663132113302401<![CDATA[Dual-Polarized Bandpass Frequency-Selective Surface With Quasi-Elliptic Response Based on Square Coaxial Waveguide]]>663133113392952<![CDATA[Systematic Design of Printable Metasurfaces: Validation Through Reverse-Offset Printed Millimeter-Wave Absorbers]]>663134013514141<![CDATA[Realization of Beam Steering Based on Plane Spiral Orbital Angular Momentum Wave]]>6631352135823013<![CDATA[A Memory Saving Augmented EFIE With Modified Basis Functions for Low-Frequency Problems]]>663135913653846<![CDATA[A Time-Domain Thin Dielectric Sheet (TD-TDS) Integral Equation Method for Scattering Characteristics of Tunable Graphene]]>663136613731878<![CDATA[Efficient Three-Step LOD-FDTD Method in Lossy Saturated Ferrites With Arbitrary Magnetization]]>663137413831473<![CDATA[The FIT-MoM Hybrid Method for Analysis of Electromagnetic Scattering by Dielectric Bodies of Revolution]]>663138413911407<![CDATA[Vector Parabolic Equation-Based Derivation of Rectangular Waveguide Surrogate Models of Arched Tunnels]]>663139214033737<![CDATA[Beyond Geometrical Optics: Higher Order Diffraction at Thin Curved Dielectric Layers]]>663140414121211<![CDATA[A Potential-Based Integral Equation Method for Low-Frequency Electromagnetic Problems]]>$Phi $ ) equation is solved in tandem with the vector potential ($textbf {A}$ ) equation. The resulting system is immune to low-frequency catastrophe and accurate in capturing the electrostatic and magnetostatic physics. The fast convergence of the new $textbf {A}$ -$Phi $ system, which is a typical symmetric saddle point problem, is made possible through the design of an appropriate left constraint preconditioner. Numerical examples validate the efficiency and stability of the novel formulation in solving both EM scattering and circuit problems over a wide frequency range up to very low frequencies.]]>663141314263159<![CDATA[Modeling the Phase Correlation of Effective Diffuse Scattering From Surfaces for Radio Propagation Prediction With Antennas at Refined Separation]]>663142714352643<![CDATA[Application of Inverse Source Reconstruction to Conformal Antennas Synthesis]]>663143614453463<![CDATA[Transmission Line Modeling of Scattering From a Linear Conductor Near the Surface of the Ground]]>663144614551436<![CDATA[Reducing the Radar Cross Section of Microstrip Arrays Using AMC Structures for the Vehicle Integration of Automotive Radars]]>663145614643062<![CDATA[Spherical Field Transformation Above Perfectly Electrically Conducting Ground Planes]]>663146514784167<![CDATA[Cell Coverage Analysis of 28 GHz Millimeter Wave in Urban Microcell Environment Using 3-D Ray Tracing]]>663147914873393<![CDATA[Far-Field Antenna Pattern Measurement Using Near-Field Thermal Imaging]]>663148814962516<![CDATA[A Model Independent Scheme of Adaptive Focusing for Wireless Powering to In-Body Shifting Medical Device]]>663149715062015<![CDATA[Multiplexing Antenna System in the Non-Far Region Exploiting Two-dimensional Beam Mode Orthogonality in the Rectangular Coordinate System]]>663150715154177<![CDATA[Prediction of Passive Intermodulation on Mesh Reflector Antenna Using Collaborative Simulation: Multiscale Equivalent Method and Nonlinear Model]]>$0.25 times 0.25,,text{m}^{2}$ at C-band and Ku-band have been established, indicating basically consistent to the measured results and validating the effectiveness of this method. Moreover, the PIM prediction of a mesh reflector antenna with the same woven structure is also given. These results show that this method can be utilized to predict PIM level of the mesh reflector antenna under conditions of the precise PIM measurement of mesh reflector sample, also providing reference for designing the low PIM microwave components.]]>663151615212021<![CDATA[Design of High-Isolation Wideband Dual-Polarized Compact MIMO Antennas With Multiobjective Optimization]]>663152215271633<![CDATA[Agile Beamwidth Control and Directivity Enhancement for Aperture Radiation With Low-Profile Metasurfaces]]>LC and split-ring resonator metasurfaces has a substantial beamwidth reduction on both principal planes and a 4.32 dBi gain enhancement around the operating frequency.]]>663152815332079<![CDATA[Ultra-Wideband Antipodal Tapered Slot Antenna With Integrated Frequency-Notch Characteristics]]>663153415391471<![CDATA[Wide Bandwidth and Enhanced Gain of a Low-Profile Dipole Antenna Achieved by Integrated Suspended Metasurface]]>$0.07lambda $ ($lambda $ is the wavelength in free space at the center operating frequency) shows the realized boresight gain of 8.5–11.5 dBi over $vert text{S}_{11}vert le -10$ dB impedance bandwidth of 33.6% (or 4.15–5.85 GHz).]]>663154015442412<![CDATA[A Low Cost and Highly Efficient Metamaterial Reflector Antenna]]>663154515481513<![CDATA[A Simple Formula Expressing the Fields on the Aperture of an Impulse Radiating Antenna Fed by TEM Coplanar Plates]]>66315491552659<![CDATA[Miniaturized Dual-Loop NFC Antenna With a Very Small Slot Clearance for Metal-Cover Smartphone Applications]]>$15,, text {mm} times 25 ,,text {mm}$ is initially proposed for full metal-cover smartphone applications. To achieve a small clearance zone on the metal cover, a small rectangular slot of size $8 ,,text {mm} times 16,, text {mm}$ is loaded into the metal cover. To allow good inductive coupling, the NFC antenna is only 0.37 mm beneath the center of the rectangular slot. Because of that, the direction of the eddy current induced on the metal cover will be the same as the dual-loop NFC antenna. It is noteworthy that the prototype NFC antenna integrated with a single rectangular slot loaded full metal cover was certified by the Europay, MasterCard, and Visa test.]]>663155315581951<![CDATA[A Wideband, Unidirectional Circularly Polarized Antenna for Full-Duplex Applications]]>663155915631033<![CDATA[Reconfigurable, Wideband, Low-Profile, Circularly Polarized Antenna and Array Enabled by an Artificial Magnetic Conductor Ground]]>$1 times 4$ array of these elements were fabricated and tested. The measured results for both prototypes are in good agreement with their simulated values, validating their design principles. They are low profile with a height $sim 0.05lambda _{mathrm {mathbf {0}}}$ . The array exhibits a wide fractional operational bandwidth: 1.65 GHz (21.7%), and a high realized gain: 13 dBic. Since they would enhance their channel capacity and avoid polarization mismatch issues, these reconfigurable CP antenna systems are very suitable for modern wireless systems.]]>663156415692723<![CDATA[Radiative MRI Coil Design Using Parasitic Scatterers: MRI Yagi]]>663157015751220<![CDATA[A Sleeve-Badge Circularly Polarized Textile Antenna]]>663157615791049<![CDATA[Pattern Reconfigurable Slotted-Patch Array]]>663158015831330<![CDATA[A Novel Rotated Antenna Array Topology for Near-Field 3-D Fully Polarimetric Imaging]]>663158415892189<![CDATA[Skeletonization Accelerated MLFMA Solution of Volume Integral Equation for Plasmonic Structures]]>663159015943221<![CDATA[Isolation Enhancement and Radar Cross Section Reduction of MIMO Antenna With Frequency Selective Surface]]>663159516002650<![CDATA[An Automatic Scheme for Synthetic Basis Functions Method]]>663160116063589<![CDATA[A Coarse-Grained Integral Equation Method for Multiscale Electromagnetic Analysis]]>663160716121874<![CDATA[Evaluation of Efficient Green’s Functions for Spherically Stratified Media]]>663161316181408<![CDATA[Wide Angular Sweeping of Dynamic Electromagnetic Responses From Large Targets by MPI Parallel Skeletonization]]>663161916231035<![CDATA[Efficient Field Reconstruction Using Compressive Sensing]]>66316241627687<![CDATA[Combining FSS and EBG Surfaces for High-Efficiency Transmission and Low-Scattering Properties]]>$pi $ reflection phase cells with a chessboard distribution to reduce the backward scattering wave. As a proof-of-concept demonstration, the planar and cylindrical surfaces are, respectively, designed to verify such two functionalities. Our FSS-EBG surface can make the antenna signal transmit at S-band with small insertion loss and simultaneously provide wideband low-scattering property at X–Ku band, which is suitable to be used as the stealth antenna radome. In addition, the possibility of integrating polarization conversion function into the passing band is numerically demonstrated.]]>663162816322208<![CDATA[IEEE Transactions on Antennas and Propagation]]>663C3C3111<![CDATA[Institutional Listings]]>663C4C4388