<![CDATA[ IEEE Transactions on Power Electronics - new TOC ]]>
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TOC Alert for Publication# 63 2018March 19<![CDATA[Table of Contents]]>337C1553162<![CDATA[IEEE Power Electronics Society]]>337C2C262<![CDATA[Hill Climbing Power Flow Algorithm for Hybrid DC/AC Microgrids]]>δ and observes the corresponding changes in the active power. An average model of the hybrid microgrid is first developed for the evaluation of the proposed algorithm. The proposed algorithm is then applied to verify its effectiveness for achieving sufficient power exchange and enhancing the dynamic response. The model is implemented and tested using MATLAB/Simulink. Moreover, the proposed control strategy is experimentally validated using a real-time simulator, OPAL-RT.]]>337553255371105<![CDATA[A Switched-Capacitor-Based Multilevel Inverter Topology With Reduced Components]]>33755385542521<![CDATA[A Novel Seven-Level Hybrid-Clamped (HC) Topology for Medium-Voltage Motor Drives]]>33755435547711<![CDATA[An Open-Loop Grid Synchronization Approach for Single-Phase Applications]]>337554855551436<![CDATA[Small-Signal Modeling of Three-Phase Synchronous Reference Frame Phase-Locked Loops]]>33755565560455<![CDATA[Active Identification Method for Line Resistance in DC Microgrid Based on Single Pulse Injection]]>33755615564747<![CDATA[A New Inductive Power Transfer Topology Using Direct AC–AC Converter With Active Source Current Waveshaping]]>337556555771622<![CDATA[Distributed Control for a Modular Multilevel Converter]]>337557855917078<![CDATA[Hierarchical Distributed Balancing Control for Large-Scale Reconfigurable AC Battery Packs]]>337559256025523<![CDATA[Improving the Short-Circuit Reliability in IGBTs: How to Mitigate Oscillations]]>337560356121879<![CDATA[Combined Multilevel and Two-Phase Interleaved LLC Converter With Enhanced Power Processing Characteristics and Natural Current Sharing]]>LLC converter topology with high output current applications. Compared to a conventional two-phase LLC converter, the new converter adds a single capacitor that contributes to lower voltage stress on the primary side's switches, automatically balances the current distribution between the phases, and enhances the power processing capabilities. All the attractive features of LLC converters are preserved, such as zero-voltage switching on the primary side's mosfets, zero-current switching on the secondary side's power devices, narrow switching frequency range, and simple design. Full principle of operation and analysis of the converter are described, as well as the converter's primary characteristics and the impact of nonideal components on the current sharing behavior. A 600 W, 400 V-to-12 V experimental prototype is used as a showcase of the attractive features of the new converter, demonstrating excellent current sharing, simple implementation, and high efficiency of up to 97.3%.]]>337561356202576<![CDATA[Common-Mode Voltage Elimination for Variable-Speed Motor Drive Based on Flying-Capacitor Modular Multilevel Converter]]>337562156281408<![CDATA[Capacitor Voltage Balance Control of Five-Level Modular Composited Converter With Hybrid Space Vector Modulation]]>$M,< ,0.5$ ) and a simplified vector synthesis method for the high-modulation region ($Mgeq 0.5$). The proposed hybrid modulation maintains the dc capacitor voltage balance over the full modulation range and power factor. Finally, the effectiveness of the proposed HSVM strategy is verified with the simulation and experimental results.]]>337562956401526<![CDATA[The Alternate Arm Converter (AAC)—“Short-Overlap” Mode Operation—Analysis and Design Parameter Selection]]>337564156594344<![CDATA[High-Frequency EMI Attenuation at Source With the Auxiliary Commutated Pole Inverter]]> $dvtext{/} dt$ and $ditext{/} dt$ slew rates, can be addressed through waveform-shaping techniques. For example, while most soft-switching converters can reduce switching loss, they do so by switching the semiconductor devices in a slower and smoother manner, resulting in the attenuation of high-frequency harmonics. This paper examines the auxiliary commutated pole inverter (ACPI) topology, and its first contribution is the attenuation of the high-frequency content of its EMI source, that is, the output voltage, in a predictable manner, through the active control of the resonant circuit. This is achieved by first, discussing the time-domain characteristics of trapezoidal and S-shaped pulse-trains that lead to attenuated high-frequency harmonic content, and second, by analyzing the equivalent LC circuit of the ACPI. The design of the inverter is then focused on the active control of the resonant parameters, for a predetermined and enhanced output voltage high-frequency response. The second contribution of this paper is the comparison of the EMI performance of hard switching and of three soft-switching modes, fixed-timing control, variable-timing control, and capacitive turn-offs, and how this informs important metrics such as power efficiency, current stress, and implementation complexity. Finally, the third contribution is on the trade-offs that arise when the primary design goal is enhanced EMI pe-
formance as opposed to switching loss reduction. A 5-kW, 3-phase ACPI prototype is used for validating the high-frequency content attenuation at source. It is shown that the ACPI can achieve a 37 dB harmonic attenuation of its output voltage at 4 MHz, compared to a hard-switched inverter.]]>337566056761785<![CDATA[An Instantaneously Triggered Short-Circuit Protection Architecture for Boost Switching DC/DC Converters]]>337567756851347<![CDATA[Imbalance Mechanism and Balanced Control of Capacitor Voltage for a Hybrid Modular Multilevel Converter]]>337568656965190<![CDATA[Optimized Control of the Modular Multilevel Converter Based on Space Vector Modulation]]>$2n+ 1$, where $n$ is the number of submodules in the upper or lower arm of each phase) of output phase voltages, but also leads to an optimized control performance in terms of capacitor voltage balancing, circulating current suppression, and common-mode voltage reduction. The maximum level number is achieved by introducing a new equivalent circuit of the MMC, and the optimized control is obtained by selecting the optimal redundant switching states. Since the computational burden of the SVM scheme is independent of the voltage level number, the proposed method is well suited to the MMC with any number of submodules. Simulation and experimental results are presented to validate the proposed method.]]>337569757112021<![CDATA[A New Voltage Measure Method for MMC Based on Sample Delay Compensation]]>337571257233317<![CDATA[Design of a 10-kV·A Soft-Switching Solid-State Transformer (S4T)]]>337572457382715<![CDATA[Loss Optimization of MMC by Second-Order Harmonic Circulating Current Injection]]>337573957533667<![CDATA[New Modeling Method and Design Optimization for a Soft-Switched DC–DC Converter]]>337575457722974<![CDATA[Custom Power Active Transformer for Flexible Operation of Power Systems]]>337577357831651<![CDATA[Achieving Multiple Functions of Three-Phase Electric Springs in Unbalanced Three-Phase Power Systems Using the Instantaneous Power Theory]]>337578457952150<![CDATA[A Family of Gradient Descent Grid Frequency Estimators for the SOGI Filter]]>337579658102695<![CDATA[Active Junction Temperature Control of IGBT Based on Adjusting the Turn-off Trajectory]]>337581158232287<![CDATA[Multiple-Vector Model-Predictive Power Control of Three-Phase Four-Switch Rectifiers With Capacitor Voltage Balancing]]>337582458352060<![CDATA[Direct Power Control of Doubly Fed Induction Generator Without Phase-Locked Loop Under Harmonically Distorted Voltage Conditions]]>337583658461858<![CDATA[Lithium–Sulfur Battery State-of-Charge Observability Analysis and Estimation]]>337584758591344<![CDATA[DC–DC Converter Based Photovoltaic Simulator With a Double Current Mode Controller]]>337586058681346<![CDATA[Novel Control Method for Multimodule PV Microinverter With Multiple Functions]]>337586958792397<![CDATA[Synthesis and Comparative Analysis of Very High Step-Up DC–DC Converters Adopting Coupled-Inductor and Voltage Multiplier Cells]]>337588058972736<![CDATA[Low Dissipative Snubber Using Flyback-Type Transformer for 10 kV IGCT in 7 MW Wind Turbine Systems]]>di/dt snubber circuit according to the PLECS magnetic simulation of three-level neutral point clamped grid side converter. The experiments are performed using IGCT stack. Flyback transformer yields the effectiveness of the proposed snubber in wind turbine systems.]]>337589859081686<![CDATA[Nonlinear Capacitance Evolution of Lithium-Ion Capacitors Based on Frequency- and Time-Domain Measurements]]>337590959161011<![CDATA[Voltage-Lift Technique Based Nonisolated Boost DC–DC Converter: Analysis and Design]]>33759175926841<![CDATA[New Switching Strategy for Single-Mode Operation of a Single-Stage Buck–Boost Inverter]]>337592759363887<![CDATA[Multi-Input Switched-Capacitor Multilevel Inverter for High-Frequency AC Power Distribution]]>337593759481260<![CDATA[A Dual Active Bridge Converter With an Extended High-Efficiency Range by DC Blocking Capacitor Voltage Control]]>337594959667676<![CDATA[High-Efficiency High Step-Up DC–DC Converter With Dual Coupled Inductors for Grid-Connected Photovoltaic Systems]]>337596759822188<![CDATA[Voltage-Double Magnetically Coupled Impedance Source Networks]]>337598359942103<![CDATA[Research on a 4000-V-Ultrahigh-Input-Switched-Mode Power Supply Using Series-Connected MOSFETs]]>337599560112336<![CDATA[Zero-Voltage and Zero-Current Switching PWM DC–DC Converter Using Controlled Secondary Rectifier With One Active Switch and Nondissipative Turn-Off Snubber]]>337601260232410<![CDATA[Resonant Multi-input/Multi-output/Bidirectional ZCS Step-Down DC--DC Converter With Systematic Synthesis for Point-to-Point Power Routing]]>337602460321484<![CDATA[Voltage Gain Improvement of a High-Step-Down Converter With Coupled-Inductor Core Size Reduction Based on Flux Linkage]]> mosfet, the flux linkage of the coupled inductor can be decreased, and hence the required core size can be reduced. In addition, due to the auxiliary circuit, the voltage spike across the tapped switch can be reduced. Above all, the step-down gain can be improved. Finally, detailed theoretical analyses and experimental results are provided to verify the feasibility and effectiveness of the proposed converter.]]>337603360472130<![CDATA[Influence of Temperature on the Pressure Distribution Within Press Pack IGBTs]]>337604860592132<![CDATA[Investigation of Spatial Harmonic Magnetic Field Coupling Effect on Torque Ripple for Multiphase Induction Motor Under Open Fault Condition]]>337606060712458<![CDATA[An Ultralow Loss Inductorless $dv/dt$ Filter Concept for Medium-Power Voltage Source Motor Drive Converters With SiC Devices]]>$dv/dt$ filter is presented targeted for 100-kW to 1-MW voltage source converters using silicon carbide (SiC) power devices. This concept uses the stray inductance between the power device and the converter output as a filter component in combination with an additional small RC-link. Hence, a lossy, bulky, and costly filter inductor is avoided and the resulting output $dv/dt$ is limited to 5–10 kV/$mu$s independent of the output current and switching speed of the SiC devices. As a consequence, loads with $dv/dt$ constraints, e.g., motor drives can be fed from SiC devices enabling full utilization of their high switching speed. Moreover, a filter-model is proposed for the selection of filter component values for a certain $dv/dt$ requirement. Finally, results are shown using a 300-A 1700-V SiC metal–oxide–semiconductor field-effect transistor (mosfet). These results show that the converter output $dv/dt$ can be limited to 7.5 kV/ $mu$s even though values up to 47 kV/ $mu$s were measured across the SiC mosfet module. Hence, the total switching losses, including the filter losses, are verified to be three times lower compared to when the mosfet$dv/dt$ was slowed down by adjusting the gate driver.]]>337607260811564<![CDATA[A Prediction-Based Current Sampling Scheme Using Three Resistors for Induction Motor Drives]]>337608260924106<![CDATA[Comparison of Tripolar and Circular Pads for IPT Charging Systems]]>337609361031669<![CDATA[A Combining FPE and Additional Test Vectors Hybrid Strategy for IPMSM Sensorless Control]]>337610461132088<![CDATA[Development of a Prime Mover Emulator Using a Permanent-Magnet Synchronous Motor Drive]]>337611461252853<![CDATA[An Improved IGBT Short-Circuit Protection Method With Self-Adaptive Blanking Circuit Based on V CE Measurement]]>$V_{CE}$ measurement detects the collector–emitter voltage of an IGBT to determine whether the IGBT short-circuit fault occurs. The blanking circuit is needed in this kind of protection method to avoid the false triggering of the short-circuit protection during IGBT turn-on transient. However, this blanking circuit should be carefully designed for different types of IGBT modules. In order to make the IGBT short-circuit protection circuit suitable for the tolerance of IGBT modules, a self-adaptive blanking circuit combined with the aforementioned short-circuit protection method based on $V_{CE}$ measurement is proposed. The proposed method is achieved by feeding back the required minimum blanking time interval which is decided by comparing the desaturation reference voltage with the collector–emitter voltage. The short-circuit protection delay time for the conventional circuit and the proposed circuit are compared. Experimental results are included to prove the effectiveness of the proposed circuit.]]>337612661361537<![CDATA[Communication Functions for a Gate Driver Under High Voltage and High dv/dt]]>mosfet or IGBT transistors is carried out by a dedicated circuit called « driver », which is located as close as possible to the power module. It transmits switch-on and switch-off orders coming from the control unit and ensures the integrity of the component through safety functions. It also provides a galvanic isolation essential to guarantee the effective functioning of the system and the users’ safety. Switching times of SiC mosfet are faster than Si IGBT, and SiC mosfet can also work under a greater dc voltage than Si mosfet. This involves the presence of higher dv/dt in the converter. In this paper, a communication function is studied to be integrated into the new generations of drivers for SiC mosfet . The interest of the implementation of a communication system in a driver is presented. Currently available solutions on the market to provide isolation to communication channels are debated. The theoretical development of a solution called « CAN-ISO » is detailed and experimental results under a high peak voltage of 2 kV and a high dv/dt equal to ${text{125}};{text{kV}}/{mu}{text{s}}$ are presented.]]>337613761461735<![CDATA[Analytical Technique for Evaluating Stray Capacitances in Multiconductor Systems: Single-Layer Air-Core Inductors]]>337614761581455<![CDATA[Single-Phase LED Drivers With Minimal Power Processing, Constant Output Current, Input Power Factor Correction, and Without Electrolytic Capacitor]]>337615961701639<![CDATA[Switched-Capacitor-Based Current Compensator for Mitigating the Effect of Long Cable Between PWM Driver and LED Light Source]]>337617161862329<![CDATA[A Constant-on-Time Control DC–DC Buck Converter With the Pseudowave Tracking Technique for Regulation Accuracy and Load Transient Enhancement]]>337618761981621<![CDATA[A High-Bandwidth Integrated Current Measurement for Detecting Switching Current of Fast GaN Devices]]>337619962105111<![CDATA[Thermal Impedance Meter for Power <sc>mosfet</sc> and IGBT Transistors]]>mosfets and IGBT transistors, and measurement results are described. The measurements were performed by generic modulation method that implies heating a device under test by power varying harmonically. A pulse sequence of heating current, with the pulse length varying harmonically, is passed through the device under test. The p-n junction temperature is determined by measuring a temperature-sensitive parameter, which is forward voltage drop on the p-n junction between heating pulses at low measuring current. Analysis of the dependence of thermal impedance on modulation frequency allows us to determine thermal impedance components corresponding to the structural elements of the object under test. The method allows us to significantly reduce the effect of heating the device's case during the measurement, and thereby increase the accuracy of thermal resistance measurement.]]>33762116216771<![CDATA[Separation of Wear-Out Failure Modes of IGBT Modules in Grid-Connected Inverter Systems]]>I– V characterizations of IGBT modules. Further, only one monitoring parameter is used, and thus, it is cost-effective compared with using one more monitoring parameter in order to separate failure modes. Experimental results verify the validity and feasibility of the proposed method.]]>33762176223732<![CDATA[An Isolated Quasi-Resonant Multiphase Single-Stage Topology for 48-V VRM Applications]]>$mu$ m lithography together with a digital pulse-width-modulation with a 195 ps resolution, and a 40 MS/s, 7-bit ADC. Experimental results show an efficiency of 93.1% for a 250 A, 1.8 V VRM, and of 93.2% for a 102 A, 1.2-V double data rate (DDR) power supply.]]>337622462372279<![CDATA[Optimized Switching Repetitive Control of CVCF PWM Inverters]]>$Q$ can be applied to reduce the tracking error. The stability analysis and optimized design procedure are also given. Comparative experiments in different load situations are performed to demonstrate the validity of the proposed scheme.]]>337623862471448<![CDATA[Mitigation of Grid-Current Distortion for LCL-Filtered Voltage-Source Inverter With Inverter-Current Feedback Control]]>LCL filters feature low inductance; thus, the injected grid current from an LCL -filtered voltage-source inverter can be easily distorted by grid-voltage harmonics. This problem is especially tough for the control system with inverter-side current feedback (ICF), since the grid-current harmonics can freely flow into the filter capacitor. In this case, because of the loss of harmonic information, traditional harmonic controllers fail to mitigate the grid-current distortion. Although this problem may be avoided using the grid-voltage feedforward scheme, the required differentiators may cause the noise amplification. In light of the above issue, this paper develops a simple method for the ICF control system to mitigate the grid-current harmonics without extra sensors. In the proposed method, resonant harmonic controllers and an additional compensation loop are adopted at the same time. The potential instability introduced by the compensation loop can be avoided through a special design of the compensation position. Finally, the effectiveness of the proposed method for harmonic rejection is verified by detailed experimental results.]]>337624862611924<![CDATA[An Integral Droop for Transient Power Allocation and Output Impedance Shaping of Hybrid Energy Storage System in DC Microgrid]]>V-P droop, the transient power allocation in HESSs can be intrinsically realized in a decentralized manner. The high-frequency components of power demand can be compensated by the ESs with ID, whereas the ESs with V-P droop respond to the smooth change of load power. Additionally, the ID coefficient can be designed according to the nominal ramp rate of the ESs with slow response, which helps to extend the lifespan of the HESS. On the other hand, to easily assess the stability of the system feeding constant power loads, a minimum relative impedance criterion (MRIC) is developed. Based on MRIC, it is revealed that the proposed ID can shape the output impedance of the HESS and stabilize the entire system. The feasibility and effectiveness of ID are verified by both simulations and experimental results.]]>337626262772655<![CDATA[Buck–Boost Dual-Leg-Integrated Step-Up Inverter With Low THD and Single Variable Control for Single-Phase High-Frequency AC Microgrids]]>M becomes the only control variable to regulate the output voltage/current and the control is simplified. The THD of the proposed inverter output can remain low throughout the entire input voltage range and load power range. This paper presents the topology derivation procedure, operation principle, and steady-state characteristics of the proposed inverter. To validate the effectiveness of theory, experimental results of a 400 W hardware prototype, where the output voltage frequency is at 500 Hz, are reported.]]>337627862912393<![CDATA[Limitations and Accuracy of a Continuous Reduced-Order Model for Modular Multilevel Converters]]>337629263031282<![CDATA[Model Predictive Control of Power Converters for Robust and Fast Operation of AC Microgrids]]>337630463172431<![CDATA[Analysis and Control of Direct Voltage Regulated Active DC-Link Capacitance Reduction Circuit]]>337631863322068<![CDATA[Stability Analysis of Digital-Controlled Single-Phase Inverter With Synchronous Reference Frame Voltage Control]]>337633363502327<![CDATA[Dynamic Improvement of Series–Series Compensated Wireless Power Transfer Systems Using Discrete Sliding Mode Control]]>337635163601596<![CDATA[Second-Harmonic Current Reduction for Two-Stage Inverter With Boost-Derived Front-End Converter: Control Schemes and Design Considerations]]>$(2f_{{rm{o}}})$, generating notorious second-harmonic current (SHC) in the front-end dc–dc converter and the input dc voltage source. This paper focuses on the SHC reduction for a two-stage single-phase inverter with boost-derived front-end converter. To reduce the SHC, a virtual series impedance, which has high impedance at $2f_{{rm{o}}}$ while low impedance at other frequencies, is introduced in series with the boost diode or the boost inductor to increase the impedance of the boost-diode branch or boost-inductor branch at $2f_{{rm{o}}}$. Meanwhile, for achieving good dynamic performance, a virtual parallel impedance, which exhibits infinite impedance at $2f_{{rm{o}}}$ while low impedance at other frequencies, is introduced in parallel with the dc-bus capacitor to reduce the output impedance of the boost-derived converter at the frequencies except for $2f_{{rm{o}}}$. The virtual series impedance is realized by the feedback of the boost-diode current or the boost-inductor current, while the virtual parallel impedance is implemented by the feedback of the dc-bus voltage. Based on the virtual-impedance approach, a variety of SHC reduction control schemes are derived. A step-by-step closed-loop parameters design approach with considerations of reducing the SHC and improving the dynamic performance is also proposed for the derived SHC reduction control schemes. Finally, a 1-kW prototype is built and tested, and experimental results are presented to verify the effectiveness of the propos-
d SHC reduction control schemes.]]>337636163784905<![CDATA[Reconfigurable Wireless Power Transfer Systems With High Energy Efficiency Over Wide Load Range]]>337637963902313<![CDATA[A Dual-Coupled LCC-Compensated IPT System With a Compact Magnetic Coupler]]>LCC-compen-sated inductive power transfer system with a compact magnetic coupler to improve misalignment performance. In the magnetic coupler, the main coils form the first coupling, and compensation inductors are integrated with the main coils to form a second coupling. In the design presented in this paper, the main coils are unipolar and the compensation inductors are in a Double D structure. The fundamental harmonics approximation method is used to analyze the circuit, and the couplings between the main coils and compensation inductors are considered to determine the net power flow. In misalignment cases, it is shown that the coupling between the compensation inductors, and the cross couplings between the compensation inductors and main coils, contribute to increasing the system power. A 3.5 kW prototype is designed and implemented to validate the proposed dual-coupled system. The primary coil size is ${text{450 mm}times text{450 mm}}$, and the secondary coil size is ${text{300 mm}times text{300 mm}}$. Experimental results show that the proposed dual-coupled system can significantly improve the misalignment performance, and retains at least 56.8% and 82.6% of the well-aligned power at 150 mm misalignment in the x- and y-directions, respectively.]]>337639164021645<![CDATA[Current-Sensorless VSC-PFC Rectifier Control With Enhance Response to Dynamic and Sag Conditions Using a Single PI Loop]]>dq0 reference frame is not included in the control scheme. These characteristics simplify the implementation of the proposed control thus improving its efficiency. The theoretical analysis and simulation validate the technical feasibility of the proposed control, and finally, various cases of study and experimental results obtained with a laboratory scale-down prototype are presented to confirm the viability and performance of the control.]]>337640364156863<![CDATA[Distributed Nonlinear Control With Event-Triggered Communication to Achieve Current-Sharing and Voltage Regulation in DC Microgrids]]> $Vhbox{--}I$ droop controller. The proposed event-triggered-based communication strategy can considerably reduce the communication traffic and significantly relax the requirement for precise real-time information transmission, without sacrificing system performance. Experimental results obtained from a dc MG setup show the robustness of the new proposal under normal, communication failure and communication delay operation conditions. Finally, communication traffic under different communication strategies is compared, showing a drastic traffic reduction when using the proposed approach.]]>337641664336765<![CDATA[Smooth Reference Modulation to Improve Dynamic Response in Electric Drive Systems]]>337643464431847<![CDATA[Virtual Variable Sampling Discrete Fourier Transform Based Selective Odd-Order Harmonic Repetitive Control of DC/AC Converters]]>337644464521223<![CDATA[IEEE Power Electronics Society]]>337C3C353<![CDATA[Blank page]]>337C4C42