<![CDATA[ IEEE Transactions on Industry Applications - new TOC ]]>
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TOC Alert for Publication# 28 2018March 22<![CDATA[Table of Contents]]>542C1944185<![CDATA[IEEE Industry Applications Society]]>542C2C254<![CDATA[Recognition of 2017 and Paper Reviewers]]>542945976233<![CDATA[Bounds for Optimal Control of a Regional Plug-in Electric Vehicle Charging Station System]]>542977986990<![CDATA[Considering Carbon Emissions in Economic Dispatch Planning for Isolated Power Systems: A Case Study of the Taiwan Power System]]>2 equivalent model was created that accounts for the various fuel types (e.g., coal, oil, and natural gas) used in power generation. The correlation between power-generation costs and carbon emissions was determined according to CO_{2} emissions tradeoff and incremental cost–CO_{2 } reduction curves. The proposed method was applied to the Taiwan Power Company system. The results indicate that the method was effective in determining the influence of CO_{2} emissions on power-generation costs during off-peak, semi-peak, and peak hours, as well as daily load demands. The system enables the simultaneous consideration of economic and environmental benefits.]]>5429879971243<![CDATA[Bi-Directional CLLC Converter With Synchronous Rectification for Plug-In Electric Vehicles]]>CLLC converter with an integrated transformer for plug-in electric vehicle applications. To improve efficiency and power density, the integrated transformer is introduced and simulated using finite element analysis. In addition, synchronous rectification is implemented by controlling the turn-on and turn-off timings based on the phase difference between primary gate pulse and secondary resonant current. Furthermore, a simplified closed-loop design is discussed and implemented on a digital signal processor (TMS320F28335). The effectiveness of the control loop is verified through a 3.3 kW proof-of-concept prototype with peak efficiency of 97.5%.]]>54299810051256<![CDATA[Practical Model for Energy Consumption Analysis of Beam Pumping Motor Systems and Its Energy-Saving Applications]]>542100610161789<![CDATA[Multi-Objective Optimization Model of Source–Load–Storage Synergetic Dispatch for a Building Energy Management System Based on TOU Price Demand Response]]>542101710281270<![CDATA[Ultra-Short-Term Wind Generation Forecast Based on Multivariate Empirical Dynamic Modeling]]>54210291038887<![CDATA[The Role of Demand Response as an Alternative Transmission Expansion Solution in a Capacity Market]]>54210391046862<![CDATA[Fuzzy-Secondary-Controller-Based Virtual Synchronous Generator Control Scheme for Interfacing Inverters of Renewable Distributed Generation in Microgrids]]>542104710611689<![CDATA[Rotor-Current-Based Fault Diagnosis for DFIG Wind Turbine Drivetrain Gearboxes Using Frequency Analysis and a Deep Classifier]]>54210621071876<![CDATA[Sensor Fault Detection and Isolation for a Wireless Sensor Network-Based Remote Wind Turbine Condition Monitoring System]]>54210721079791<![CDATA[A Modified Bus-Split Method for Aggregating Distributed Generation Units]]>$1phi$ or a $3phi$ distribution network. The modified bus-split aggregation method can be beneficial for determining possible offsets of conventional power generation, as well as improving the management of peak-demand conditions. The injected power-based bus-split aggregation method is implemented for performance testing using collected data from several wind and photovoltaic energy conversion systems, which are interconnected at different locations of the distribution network. Test results demonstrate accurate and reliable aggregation without sensitivity to the interface type, power ratings, location, voltage level at the interconnection node, and/or configuration ($1phi$ or $3phi$).]]>542108010911570<![CDATA[The Formulation of a Power Flow Using $dtext{--}q$ Reference Frame Components—Part II: Unbalanced $3phi$ Systems]]> $dtext{--}q$-axis power flow (DQPF) method to analyze power systems that have buses with unbalanced $3phi$ voltages. The extended DQPF method is based on converting a $3phi$ system into three networks, which are defined using the $d$-axis, $q$-axis, and 0-axis voltage and current components. Each of the three networks is modeled by nodal equations, where the nodal voltages and admittance matrix determine the currents flowing in that network. Moreover, the apparent power mismatches are used (instead of active and reactive power mismatches) in order to reduce computational requirements. This approach offers an accurate representation of buses with unbalanced $3phi$ voltages resulting from load unbalances or asymmetrical impedances of $3phi$ transmission lines. The extended DQPF method is implemented for performance testing on different power systems that have buses with unbalanced $3phi$ voltages. Performance results show good accuracy, fast convergence, and minor sensitivity to the source of voltage unbalance. In addition, performance results reveal that the extended DQPF requires less iterations and lower memory requirements to obtain power flow solutions than other methods.]]>54210921107455<![CDATA[Harmonics and Decaying DC Estimation Using Volterra LMS/F Algorithm]]>542110811182173<![CDATA[Design and Control of Autonomous Wind–Solar System With DFIG Feeding 3-Phase 4-Wire Loads]]>542111911271912<![CDATA[A Comparative Study Between PI and Type-II Compensators for H-Bridge PFC Converter]]>54211281135914<![CDATA[ISOGI-Q Based Control Algorithm for a Single Stage Grid Tied SPV System]]>542113611453289<![CDATA[Experimental Investigation of Magnetic Field Shielding Techniques and Resulting Current Derating of Underground Power Cables]]>542114611541341<![CDATA[Optimal Coordination of Overcurrent Relays Using Gravitational Search Algorithm With DG Penetration]]>542115511651520<![CDATA[Performance of Multiframe Digital Interconnection Protection for Distributed Cogeneration Systems]]>$d!-!q$-axis components of the instantaneous $3phi$ apparent powers determined at PCC. The detection of faults, on either side of PCC, is achieved by extracting the magnitudes and phases of the high-frequency contents present in PCC currents. The high-frequency contents present in PCC currents are extracted by a phaselet filter bank that is composed of six digital high-pass filters, which are designed to implement six phaselet subframes. The multiframe digital interconnection protection is experimentally tested on a 3.6 kVA cogeneration system for islanding events, different faults on both sides of PCC, and nontransient conditions. Test results demonstrate the ability of the proposed interconnection protection to initiate accurate, fast, and reliable responses to various types of transient disturbances.]]>542116611812491<![CDATA[Ultrafast Transmission Line Fault Detection Using a DWT-Based ANN]]>54211821193574<![CDATA[A Review of Communication Failure Impacts on Adaptive Microgrid Protection Schemes and the Use of Energy Storage as a Contingency]]>542119412071220<![CDATA[Hardware and Software Integration as a Realist SCADA Environment to Test Protective Relaying Control]]>542120812172127<![CDATA[Optimal Settings for Multiple Groups of Smart Inverters on Secondary Systems Using Autonomous Control]]>542121812231111<![CDATA[Reliable Detection of Rotor Bars Breakage in Induction Motors via MUSIC and ZSC]]>542122412341115<![CDATA[Experimental Determination of Specific Power Losses and Magnetostriction Strain of Grain-Oriented Electrical Steel Coils]]>542123512441389<![CDATA[Self-Excitation Criteria of the Synchronous Reluctance Generator in Stand-Alone Mode of Operation]]>q-axis flux linkage that can lead to demagnetization of the core and consequent failure in the terminal voltage build-up. This paper studies the effects of these starting conditions on the self-excitation phenomenon and presents criteria in terms of minimum residual flux and maximum start-up acceleration to trigger self-excitation without the risk of core demagnetization. The criteria to ensure the self-excitation for synchronous reluctance machines is developed using the dq-model of the machine and the energetic model. The developed concept is also applicable to other SynRGs operating in stand-alone mode.]]>54212451253878<![CDATA[Design Comparison of NdFeB and Ferrite Radial Flux Surface Permanent Magnet Coaxial Magnetic Gears]]>542125412631333<![CDATA[Axial Vibration Suppression by Field Flux Regulation in Two-Axis Actively Positioned Permanent Magnet Bearingless Motors With Axial Position Estimation]]>d-axis current is proposed. The damping force is generated by d-axis current regulation. In this proposed method, the rotor axial position is estimated from the flux linkage variation in the motor winding. Therefore, an additional displacement sensor is not necessary. In experiments, it is confirmed that the rotor axial vibration is successfully suppressed by the proposed method.]]>542126412721917<![CDATA[Enactment-Based Direct-Drive Test of a Novel Radial-Gap Helical RotLin Machine]]>542127312821989<![CDATA[Induction Machine Drive Design for Enhanced Torque Profile]]>542128312911164<![CDATA[Analysis and Design Recommendations to Mitigate Demagnetization Vulnerability in Surface PM Synchronous Machines]]>542129213011022<![CDATA[Demagnetization Withstand Capability Enhancement of Surface Mounted PM Machines Using Stator Modularity]]>d-axis inductance and the potential peak short-circuit current is analyzed for different slot/pole number combinations. It is found that the flux gaps will affect both d-axis inductance and open-circuit flux linkage, and hence reduce short-circuit current of machines with pole number (2p) smaller than slot number (N_{s}), while they will increase the short-circuit current of machines with 2p > N_{s }. However, the opposite phenomena can be observed for demagnetization withstand capability. For machines having 2p < N_{s}, the flux gaps tend to lower withstand capability, while for machines having 2p > N_{s}, this capability can be improved. Other parameters such as magnet thickness and temperature have also been accounted for in the demagnetization analysis. Tests have been carried out to validate the predictions of inductances and short-circuit current, as well as performance such as phase back electromotive force, cogging torque, and static torque for machines with one defective magnet, which represents the case of partially demagnetized magnets.]]>542130213111282<![CDATA[Winding Thermal Model for Short-Time Transient: Experimental Validation in Operative Conditions]]>vice versa, for the prediction of the maximum time duration of the overload maintaining the winding temperature within the limit imposed by the class of insulation. The thermal model has been validated using two different electrical machines. The first one is a 10-kW automotive starter-generator prototype for mini-hybrid powertrain equipped with distributed bar windings, while the second one is a 2.2 kW total enclosed fan cooled industrial induction motor equipped with conventional stranded wire windings. Depending on the application for both machines, a short-duty transient operation in overload conditions could be required. In particular, the automotive starter-generator must accomplish engine cranking and torque assistance during the vehicle acceleration and braking, while the industrial induction machine could operate in intermittent service in overload conditions when used in machine tool applications. As a consequence, an accurate stator winding temperature prediction is mandatory to fully exploit the machine performance. For both motors, the thermal model parameters have been evaluated by fast experimental approach, and, subsequently, the model has been validated during operative overload conditions.]]>542131213191621<![CDATA[Analysis of Fractional-Slot Concentrated Winding PM Vernier Machines With Regular Open-Slot Stators]]>3 and the power factor is 0.91.]]>542132013305076<![CDATA[A Magnetic Gearbox With an Active Region Torque Density of 239 N·m/L]]>542133113382408<![CDATA[Hybrid Excitation Stator PM Vernier Machines With Novel DC-Biased Sinusoidal Armature Current]]>542133913482302<![CDATA[A Fault-Tolerant Machine Drive Based on Permanent Magnet-Assisted Synchronous Reluctance Machine]]>542134913592775<![CDATA[Investigation of Self-Excited Synchronous Reluctance Generators]]>$dq$ reference frame is developed to recognize the steady state of the self-excited reluctance generator considering no-load and resistive load conditions. A fast method to estimate the minimum capacitance requirement is proposed. Experiments have been carried out to verify the analytical results. After that, attention is paid to the capability of self-excitation in the reluctance generator with different residual magnetisms in the rotor. Different levels of residual rotor magnetism are achieved by different magnetizing dc currents. An indicative value of phase current is defined to determine the self-excitation and the required minimum residual rotor magnetism for self-excitation in the reluctance generator connected with different capacitances is discussed. At last, the capability of self-excitation in the reluctance generator by connecting charged capacitors is investigated.]]>542136013692196<![CDATA[Dynamic Testing Characterization of a Synchronous Reluctance Machine]]>54213701378983<![CDATA[Comparison Between Single-Model and Multimodel Optimization Methods for Multiphysical Design of Electrical Machines]]>542137913891128<![CDATA[Design and Demonstration of a Wound Field Synchronous Machine for Electric Vehicle Traction With Brushless Capacitive Field Excitation]]>542139014031573<![CDATA[Design and Comparison of Cascaded H-Bridge, Modular Multilevel Converter, and 5-L Active Neutral Point Clamped Topologies for Motor Drive Applications]]>54214041413752<![CDATA[Impact of Dead Time on Inverter Input Current, DC-Link Dynamics, and Light-Load Instability in Rectifier-Inverter-Fed Induction Motor Drives]]>542141414242723<![CDATA[Asymmetric Space Vector Modulation for PMSM Sensorless Drives Based on Square-Wave Voltage-Injection Method]]>542142514361712<![CDATA[A Robust Current Control Based on Proportional-Integral Observers for Permanent Magnet Synchronous Machines]]>542143714472148<![CDATA[Model-Based Sensorless Control of an IPMSM With Enhanced Robustness Against Load Disturbances Based on Position and Speed Estimator Using a Speed Error]]>542144814591919<![CDATA[Increasing the Robustness of Large Electric Driven Compressor Systems During Voltage Dips]]>542146014681237<![CDATA[A Variable Switching Point Predictive Current Control Strategy for Quasi-Z-Source Inverters]]>$^2$CC) for the quasi-Z-source inverter (qZSI). The proposed VSP $^2$CC aims to remove the output current error on the ac side, as well as the inductor current and capacitor voltage errors of the quasi-Z-source network on the dc side of the converter. Unlike the previously presented direct model predictive control (MPC) strategies for the qZSI, the proposed control scheme can directly apply the switching signals not only at the discrete time instants, but at any time instant within the sampling interval. Consequently, the shoot-through state can be applied for a shorter time than the sampling interval, resulting in lower output and inductor currents ripples. Experimental results based on field programmable gate array are provided to verify the effectiveness of the introduced control method. As it is shown, the proposed method leads to lower inductor current ripples and less output current total harmonic distortion when compared with the conventional direct MPC.]]>542146914801270<![CDATA[Stabilization and Performance Preservation of DC–DC Cascaded Systems by Diminishing Output Impedance Magnitude]]>542148114891328<![CDATA[Cascaded Open-End Winding Transformer Based DVR]]>$K$-stages is presented as well. The proposed configuration is named DVR-cascaded open-end winding (COEW). Such a topology permits a generation of a maximized number of voltage levels per converter leg. An alternative solution with multiple dc-links (i.e., multiple dc sources), named DVR-MSCOEW, is briefly introduced. The multilevel waveforms at the output voltages of the converter are generated by using a suitable pulse-width modulation (PWM) strategy associated with both dc-link voltage and transformers turns ratios. In the scenario, where common mode currents (CMC) for DVR-COEW are introduced, and if such currents are significant, a modified PWM strategy is described to compensate for CMC issues. Since it uses two-level cells, the modularity feature makes the proposed DVR-COEW an attractive solution compared with some conventional configurations. Modeling and PWM control are addressed in this paper. Simulation and experimental results are presented.]]>542149015013423<![CDATA[High-Resolution Converter for Battery Impedance Spectroscopy]]>542150215121161<![CDATA[Thermal Stress Based Model Predictive Control of Electric Drives]]>542151315223575<![CDATA[Isolated Single-Phase Matrix Converter Using Center-Tapped Transformer for Power Decoupling Capability]]>542152315312394<![CDATA[Simultaneous Selective Harmonic Elimination and THD Minimization for a Single-Phase Multilevel Inverter With Staircase Modulation]]>542153215411503<![CDATA[The Steady-State DC Gain Loss Model, Efficiency Model, and the Design Guidelines for High-Power, High-Gain, Low-Input Voltage DC–DC Converter]]>$R_d$), where $R_d$ is load, transformer turns ratio and frequency dependent. The PMRTC converter enables operation at a higher switching frequency due to the soft-switching nature, thereby achieving better power density. For battery fed high-power, high-gain applications, PMRTC exhibits a significant drop in the dc gain due to $R_d$ and other nonidealities, limiting the maximum frequency of operation. Thus, computing this drop and analyzing the effects of switching frequency becomes necessary in achieving the required steady-state dc gain. From the analysis, it is observed that, for a choice of switching frequency above $f_{s;{rm critical}}$, the required steady-state dc gain is not achieved for any turns ratio. Hence, to increase the switching frequency of operation of a PMRTC converter, a two-transformer configuration is adapted and with this configuration, the dc gain loss model, power loss, and efficiency model and small-signal model are established. The design guidelines on the choice of switching frequency and transformer turns ratio based on the proposed models is described. The proposed models with the presented design guidelines are validated in simulations and hardware prototype for a 1 kW PMRTC converter.]]>542154215541819<![CDATA[Circulating Resonant Current Between Integrated Half-Bridge Modules With Capacitor for Inverter Circuit Using SiC-MOSFET]]>mosfet s. As a result, the resonant current may occur in the dc side when the resonant frequency between phase legs was close to either the fundamental or the third harmonic of the switching frequency. In order to suppress the circulating resonant current, a graphite bus bar is applied to the phase-connecting bus bar. Using the graphite bus bar, the capacitor current can be reduced by 35% without any influence from the ac-side output current.]]>542155515621336<![CDATA[A Diode Bridge Rectifier With Improved Power Quality Using the Capacitive Network]]>542156315721495<![CDATA[Hybrid Bidirectional DC–DC Converter With Low Component Counts]]>542157315821213<![CDATA[An Overview and Comparison of Online Implementable SOC Estimation Methods for Lithium-Ion Battery]]>54215831591697<![CDATA[Design of Low-Inductance Switching Power Cell for GaN HEMT Based Inverter]]>542159216011707<![CDATA[Capacitor Characteristics Measurement Setup by Using B–H Analyzer in Power Converters]]>542160216133903<![CDATA[Miniature Piezoelectric Sensor for In-Situ Temperature Monitoring of Silicon and Silicon Carbide Power Modules Operating at High Temperature]]>R^{2} = 0.99, approximately) up to 250 °C, which is sufficient for monitoring temperature in both silicon and silicon carbide power modules.]]>542161416213439<![CDATA[Active Gate Driving Technique for a 1200 V SiC MOSFET to Minimize Detrimental Effects of Parasitic Inductance in the Converter Layout]]>mosfet is a suitable replacement for Si insulated gate bipolar transistors due to its improved switching behavior. However, high $di/dt$ and $dv/dt$ of SiC mosfet cause very high voltage overshoot and oscillations due to the presence of parasitic inductance in the converter layout and parasitic capacitance of the load. These undesired switching responses increase switching loss and give rise to electromagnetic interference related issues. Therefore, it is important to minimize these adverse effects in order to extract maximum benefits from SiC mosfet. This paper proposes an active gate driving technique for SiC mosfet to improve its overall switching performance in the presence of a moderately higher amount of parasitic inductance in the converter layout. It is achieved by controlling the device $di/dt$ and $dv/dt$ independently in four stages, with appropriate values of gate resistances for both turn- on and turn-off switching transient. The developed active gate driver is tested in a double-pulse test bed and a two-level voltage source inverter driving an induction motor load.]]>542162216331922<![CDATA[Optimized Power Modules for Silicon Carbide <sc>mosfet</sc>]]>mosfet is presented. It is based on printed circuit board embedded die technology and is compared with a standard power module. After considering the characteristics that contribute to optimal switching performances from the packaging point of view, both modules are characterized in terms of switching behavior and electromagnetic interference emissions. The results show better performances of the 3-D embedded die module with stray inductances below 2 nH and two times less common mode noise.]]>542163416442285<![CDATA[A Harmonics Elimination Method Using a Three-Winding Transformer for HVDC Transmission Systems]]>542164516512672<![CDATA[Challenges in Modeling of Large Synchronous Machines]]>B–H curve. A 20% variation in operational air gap between two machines of the same design resulted in over 18% difference in open-circuit voltage, particularly beyond the knee point. Reduction in permeability of the soft magnetic materials resulted in agreement between the simulation and measured results at saturation. Consequently, for large machines, the B–H curves from the Epstein measurements are insufficient and should be adjusted accordingly.]]>542165216621904<![CDATA[Current Source Generator–Converter Topology for Direct-Drive Wind Turbines]]>542166316701915<![CDATA[A DC-Link Voltage Fast Control Strategy for High-Speed PMSM/G in Flywheel Energy Storage System]]>542167116791416<![CDATA[Control of D-STATCOM During Unbalanced Grid Faults Based on DC Voltage Oscillations and Peak Current Limitations]]>542168016902856<![CDATA[Total Cost of Ownership Improvement of Commercial Electric Vehicles Using Battery Sizing and Intelligent Charge Method]]>542169117002001<![CDATA[Model Reference Adaptive Back-Electromotive-Force Estimators for Sensorless Control of Grid-Connected DFIGs]]>542170117111497<![CDATA[Two-Level Damping Control for DFIG-Based Wind Farm Providing Synthetic Inertial Service]]>542171217232231<![CDATA[On-Chip AC–DC Multiple-Power-Supplies Module for Transcutaneously Powered Wearable Medical Devices]]>542172417362530<![CDATA[An Efficiency-Optimal Control Method for Mono-Inverter Dual-PMSM Systems]]>542173717451148<![CDATA[Enhanced Frequency Response Based on Multiagent Distributed Power Agreement]]>542174617553551<![CDATA[Efficiency Improvement on LLC Resonant Converter Using Integrated LCLC Resonant Transformer]]>LLC resonant converter using the integrated LCLC resonant transformer. The conventional isolated LLC converter demands large leakage inductance to attain high power factor for the resonant tank. However, the large leakage inductance requires more turns of the transformer to sustain sufficient magnetizing inductance. As a result, high number of turns causes more copper loss and lower efficiency for the LLC resonant transformer. In order to reduce the demanded leakage inductance, a resonant capacitor can be connected in parallel to the magnetizing inductor through an auxiliary winding as an LCLC resonant transformer. Finally, the resonant transformer of a commercial 300 W LLC resonant converter is converted as an integrated LCLC resonant transformer with lower leakage inductance for efficiency comparison.]]>542175617641756<![CDATA[Analysis and Performance Evaluation of Axial Flux Permanent Magnet Motors]]>54217651772678<![CDATA[A Power-Frequency Controller With Resonance Frequency Tracking Capability for Inductive Power Transfer Systems]]>542177317831941<![CDATA[Adaptive Power Management Strategy for Effective Volt–Ampere Utilization of a Photovoltaic Generation Unit in Standalone Microgrids]]>542178417921904<![CDATA[A Quadratic Programming Based Optimal Power and Battery Dispatch for Grid-Connected Microgrid]]>542179318052702<![CDATA[A Real-Time State-Observer-Based Controller for a Stochastic Robotic Manipulator]]>n -link robot to track the desired trajectory in the presence of stochastic noise. The novel feature of the control algorithm is that it is based on $Ito^{prime }s$ stochastic calculus for the minimization of the conditional expectation of the instantaneous tracking error energy differential with respect to the feedback matrix subject to energy constraints. The proposed control algorithm enables the adaptive features for tracking of the robotic manipulator. Additionally, the effects of feedback coefficients and parametric uncertainty on the error energies of the system are also studied using sensitivity analysis. Finally, the experimental results conducted using the “Phantom Omni™ Bundle” robot manipulator demonstrate and validate the potential application of the proposed control algorithm on a real system.]]>542180618221522<![CDATA[A Model Predictive Power Control Approach for a Three-Phase Single-Stage Grid-Tied PV Module-Integrated Converter]]>542182318312042<![CDATA[Single-Stage Bridgeless LED Driver Based on a <italic>CLCL</italic> Resonant Converter]]>CLCL resonant converter for street lighting applications. The proposed single-stage topology integrates the PFC converter and the CLCL resonant converter by sharing active power switches. The bridgeless PFC converter adopts two buck–boost circuits operating in discontinuous-conduction mode to achieve input-current shaping. It uses two diodes instead of a rectifier bridge to reduce the power loss caused by the diodes. Owing to its superior soft-switching characteristics, the CLCL resonant converter is used. The proposed LED driver has superior features, such as high efficiency, near unity power factor, low total harmonic distortion, and relatively few diodes. A 100-W lab prototype is successfully implemented, and the experimental results verify the effectiveness and feasibility of the proposed LED driver.]]>542183218412750<![CDATA[Basic Measures Assisting the Avoidance of Arc Flash]]>54218421847324<![CDATA[Case Study Submitting Standard Proposals to the NFPA]]>54218481850173<![CDATA[Standby Person for Electrical Tasks and Rescue Guidelines for Electrical Incident Victims]]>54218511860300<![CDATA[Transformer Energization From Low-Voltage Side With Limited Generation—Power System Constraints and Protection Considerations—A Case Study]]>54218611869921<![CDATA[Integration of Modular Process Units Into Process Control Systems]]>542187018801158<![CDATA[Application of IEC 60079-10-1 Edition 2.0 for Hazardous Area Classification]]>542188118891965<![CDATA[Power Generation Load Sharing Using Droop Control in an Island System]]>542189018981096<![CDATA[Control of Permanent Magnet Synchronous Machines for Subsea Applications]]>542189919052447<![CDATA[Switchgear Main-Tie-Main Closed-Transition Transfer Design Strategy for High Levels of Available Fault Current]]>54219061911742<![CDATA[A Guide to Matching Medium-Voltage Drive Topology to Petrochemical Applications]]>542191219201392<![CDATA[Electric Generation Condition Assessment With Electromagnetic Interference Analysis]]>542192119291727<![CDATA[Applying Arc-Resistant Technologies to Medium-Voltage Variable Frequency Drives]]>54219301937680<![CDATA[It's Good To Go Backwards—Sometimes]]>542193819431112<![CDATA[Introducing IEEE Collabratec]]>542194419441914<![CDATA[IEEE Transactions On Industry Applications]]>542C3C346<![CDATA[Information for Authors]]>542C4C4199